Motorola Cp150 Cp200 6880309n62 C Manual
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6880309N62-CJune, 2005 136-162 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry 4-5 Transmit modulation from the ASFICcmp (U451 pin 40) is applied to U201 pin 10 (MOD_IN). An electronic attenuator in the ASFICcmp adjusts overall transmitter deviation by varying the audio level applied to the synthesizer IC. Internally the audio is digitized by the Fractional-N synthesizer and applied to the loop divider to provide the low-port modulation. The audio is also routed through an internal attenuator for the purpose of balancing the low port and high port modulation and reducing the deviation by 6 dB for 12.5 kHz channels, and is available at U201 pin 41 (VCO_MOD). This audio signal is routed to the VCOs modulator. Figure 4-3. VHF Frequency Generation Unit Block Diagram 4.4.1 Fractional-N Synthesizer The Fractional-N synthesizer, shown in Figure 4-4, uses a 16.8 MHz crystal (Y201) to provide the reference frequency for the system. External components C201-C203, R202 and D201 are also part of the temperature-compensated oscillator circuit. The dc voltage applied to varactor D201 from U201 pin 25 is determined by a temperature-compensation algorithm within U201, and is specific to each crystal Y201, based on a unique code assigned to the crystal that identifies its temperature characteristics. Stability is better than 2.5 ppm over temperatures of -30 to 60 °C. Software- programmable electronic frequency adjustment is achieved by an internal DAC which provides a frequency adjustment voltage from U201 pin 25 to varactor D201. The synthesizer IC U201 further divides the 16.8 MHz signal to 2.1 MHz, 2.225 MHz, or 2.4 MHz for use as reference frequencies. It also provides a buffered 16.8 MHz signal at U201 pin 19 for use by the ASFICcmp. To achieve fast locking of the synthesizer, an internal adapt charge pump provides higher current at U201 pin 45 to quickly force the synthesizer within lock range. The required frequency is then locked by the normal mode charge pump at pin 43. A loop filter (C243-C245 and R243-R245) removes noise and spurs from the steering voltage applied to the VCO varactors, with additional filtering located in the VCO circuit. Both the normal and adapt charge pumps get their supply from the capacitive voltage multiplier made up of C221-C224 and D220-D221. Two 3 V square waves from U201 pins 14-15 provide the drive signals for the voltage multiplier, which generates 12.1 V at U201 pin 47. This voltage is filtered by C225-C228. Synthesizer U201VCOBIC U251 Voltage Multiplier Loop Filter To Mixer To PA Driver VCP Vmult1 Vmult2Aux3 MOD Out Modulating SignalRx VCO Circuit Tx VCO Circuit TRB 16.8 MHz Ref. Osc. Rx Out Tx Out Buffer Q280
June, 20056880309N62-C 4-6136-162 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry One of the auxiliary outputs of the synthesizer IC (AUX3, U201 pin 2) provides the TRB signal which determines the operating mode of the VCO, either receive or transmit. Figure 4-4. VHF Synthesizer Block Diagram 4.4.2 Voltage Controlled Oscillator (VCO) The VCOBIC (U251), shown in Figure 4-5, in conjunction with the Fractional-N synthesizer (U201) generates RF in both the receive and the transmit modes of operation. The TRB line (U251 pin 19) determines which oscillator and buffer are enabled. A sample of the RF signal from the enabled oscillator is routed from U251 pin 12 through a low pass filter, to the prescaler input of the synthesizer IC (U201 pin 32). After frequency comparison in the synthesizer, a resultant DC control voltage is used to steer the VCO frequency. When the PLL is locked on frequency, this voltage can vary between 3 V and 9 V. L251 and C251 further attenuate noise and spurs on the steering line voltage. In the receive mode, the TRB line (U251 pin 19) is low. This activates the receive VCO and the receive buffer of U251, which operate within the range of 180.85 to 206.85 MHz. The VCO frequency is determined by tank inductor L254, C253-C257, and varactor D251. The buffered RF signal at U251 pin 8 is further amplified by Q280 and applied as RX_INJ to the low-pass injection filter in the receiver front end circuit. In the transmit mode, U251-19 is driven high by U201 pin 2, enabling the transmit VCO and buffer. The 136-162 MHz RF signal from U251 pin 10 is applied as TX_INJ to the input of the transmitter circuit via matching network C290-C291 and L291. TX VCO frequency is determined by L264, C263- DATA CLK CEX MODIN V CC, 5V XTAL1 WARP PREIN VCP Reference Oscillator Voltage Multiplier Voltage Controlled Oscillator 2-Pole Loop Filter DATA (U401 Pin 100) CLOCK (U401 Pin 1) SYNTH_CS (U401 Pin 47) MOD IN (U451 Pin 40) +5V (U310 Pin 5)7 8 9 10 13,30 23 25 32 47 VMULT2 VMULT1BIAS1 SFOUTAUX3 IADAPTIOUTGND FREFOUTLOCK4 19 6,22,23,24 43 45 2 28 141540Filtered 5VSteering Line LOCK (U401 Pin 56) Prescaler InLO RF Injection TX RF Injection (First Stage of PA) FREF (U451 Pin 34) 39 BIAS241 +3V (U330 Pin 5) V DD, 3VMODOUTU201 Low Voltage Fractional-N Synthesizer 5,20,34,36 TRB VCO Mod
6880309N62-CJune, 2005 136-162 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry 4-7 C267, and varactor D261. High-port audio modulation from the synthesizer IC is applied as VCO_MOD to varactor D262 which modulates the transmit VCO. Figure 4-5. VHF VCO Block Diagram Presc RX TX Matching Network Pin 8 Pin 14 Pin 103V (U330 Pin 5) VCC BuffersU201 Pin 32 AUX3 (U201 Pin 2) Prescaler Out Pin 12 Pin 19 Pin 20 TX/RX/BS Switching Network U251 VCOBIC Rx Active Bias Tx Active Bias Pin 2 Rx-I adjustPin 1 Tx-I adjustPins 9,11,17 Pin 18Vsens Circuit Pin 15 Pin 16 TX VCO Circuit TX TankRX VCO Circuit RX TankPin 7 Vcc-Superfilter Collector/RF in Pin 4 Pin 5 Pin 6RX TX V_SF (U201 Pin 28)NC NC Vcc-Logic 3V (U330 Pin 5) Steer Line Voltage (V_STEER) Pin 13 Pin 3 TRB_IN Buffer Q280 RX INJ V_SF (U201 Pin 28) TX INJ
June, 20056880309N62-C 4-8136-162 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry Notes:
Chapter 5 146-174 MHz VHF Theory Of Operation 5.1 Introduction This chapter provides a detailed theory of operation for the radio components. Schematic diagrams for the circuits described in the following paragraphs are located in Chapter 7 of this manual. 5.2 VHF Receiver The VHF receiver covers the range of 146-174 MHz and provides switchable IF bandwidth for use with 12.5 kHz or 20/25 kHz channel spacing systems. The receiver is divided into two major blocks as shown in Figure 5-1. •Front End • Back End Figure 5-1. VHF Receiver Block Diagram 5.2.1 Receiver Front-End Incoming RF signals from the antenna are first routed through the harmonic filter and antenna switch, part of the transmitter circuitry, before being applied to the receiver front end. The receiver front end consists of a preselector filter, RF amplifier, an interstage filter, and a double-balanced first mixer. The preselector filter is a fixed-tuned 4-pole design using discrete elements (L1-L4 and C1-C9) in a series/shunt resonator configuration. It has a 3 dB bandwidth of 44 MHz, an insertion loss of 2 dB and image attenuation of 40 dB at 235 MHz, with increasing attenuation at higher frequencies. Diode CR1 protects the RF amplifier by limiting excessive RF levels. The output of the filter is matched to the base of RF amplifier Q21, which provides 18 dB of gain and a noise figure of 2 dB. Operating voltage is obtained from the 5R source, which is turned off during transmit to reduce dissipation in Q21. Current mirror Q22 maintains the operating current of Q21 DemodulatorCrystal Filter 1st Mixer RF AmpIF Amp Preselector FilterInterstage Filter Recovered Audio RSSI RX from Antenna Switch Inj Filter First LO from Synthesizer Ceramic ResonatorCer FltrSwitching4E 6E6GBW_SEL
June, 20056880309N62-C 5-2146-174 MHz VHF Theory Of Operation: VHF Receiver constant at 6.2 mA regardless of device and temperature variations, for optimum dynamic range and noise figure. The output of the RF amplifier is applied to the interstage filter, a fixed-tuned 3-pole series-coupled resonator design having a 3 dB bandwidth of 58 MHz and insertion loss of 1.8 dB. This filter has an image rejection of 42 dB at 235 MHz, with increasing attenuation at higher frequencies. The output of the interstage filter is connected to the passive double-balanced mixer consisting of components T41, T42, and CR41. This mixer has a conversion loss of 7 dB. High-side injection from the frequency synthesizer is filtered by L40-L41 and C40-C44 to remove second harmonic energy that may degrade half-IF spurious rejection performance. The injection filter has a 3 dB bandwidth of 52 MHz and an insertion loss of 1.5 dB. The filtered injection signal is applied to T42 at a level of +6 dBm. The mixer output is applied to a diplexer network (L51-L52, C51, R51) which matches the 44.85 MHz IF signal to crystal filter FL51, and terminates the mixer into 50Ω at all other frequencies 5.2.2 Receiver Back-End The receiver back end is a dual conversion design. High IF selectivity is provided by FL51, a 4-pole fundamental mode 44.85 MHz crystal filter with a minimum 3 dB bandwidth of + 6.7 kHz, a maximum 20 dB bandwidth of ±12.5 kHz, and a maximum insertion loss of 3.5 dB. The output is matched to IF amplifier stage Q51 by L53 and C93. Q51 provides 16 dB of gain and a noise figure of 1.8 dB. The dc operating current is 1 mA. The output of Q51 is applied to the input of the receiver IFIC U51. Diode CR51 limits the maximum RF level applied to the IFIC. The IFIC is a low-voltage monolithic FM IF system incorporating a mixer/oscillator, two limiting IF amplifiers, quadrature detector, logarithmic received signal strength indicator (RSSI), voltage regulator and audio and RSSI op amps. The second LO frequency, 44.395 MHz, is determined by Y51. The second mixer converts the 44.85 MHz high IF frequency to 455 kHz. Additional IF selectivity is provided by two ceramic filters, FL52 (between the second mixer and IF amp) and FL53 or FL54 (between the IF amp and the limiter input). The wider filter FL53 is used for 20/25 kHz channel spacing, and the narrower filter FL54 is used for 12.5 kHz channels. When the BW_SEL line is high, the two upper diodes in packages D51 and D52 are forward biased, selecting FL53 for 20/25 kHz channels. When the BW_SEL line is low, the two lower diodes in packages D51 and D52 are forward biased, selecting FL54 for 12.5 kHz channels. Ceramic resonator Y70 provides phase vs. frequency characteristic required by the quadrature detector, with 90 degree phase shift occurring at 455 kHz. Buffer Q70 provides a lower driving impedance from the limiter to the resonator, improving the IF waveform and lowering the distortion of the recovered audio signal. The recovered audio level at the DEMOD output is 120 mV rms (25 kHz channel, 3 kHz deviation) or 60 mV rms (12.5 kHz channel, 1.5 kHz deviation). An additional RSSI output provides a DC voltage level that is proportional to RF signal level. This voltage is measured by an A/D converter contained in the microprocessor (PE4_AN4, U401 pin 63).FL52 FL53 FL54 Number of Elements:466 Insertion Loss: 4 dB 4 dB 4 dB 6 dB Bandwidth:15 kHz15 kHz9 kHz 50 dB Bandwidth: 30 kHz 30 kHz 22 kHz Stopband Rejection:27 dB47 dB47 dB
6880309N62-CJune, 2005 146-174 MHz VHF Theory Of Operation: VHF Transmitter 5-3 5.3 VHF Transmitter The VHF transmitter covers the range of 146-174 MHz. Depending on model, the output power of the transmitter is either switchable on a per-channel basis between high power (5 watts) and low power (1 watt), or is factory preset to 2 watts. The transmitter is divided into four major blocks as shown in Figure 5-2. • Power Amplifier • Harmonic Filter • Antenna Matching Network • Power Control Figure 5-2. VHF Transmitter Block Diagram 5.3.1 Transmit Power Amplifier The transmitter power amplifier has three stages of amplification. The first stage, Q100, operates in Class AB from the 5T source. It provides 13 dB of gain and an output of 20 mW. The current drain is typically 25mA. Components C105-C107 and L103 match the output of Q100 to the 50Ω input of the module U110. U110 is a two stage Silicon MOS FET power amplifier module. Drain voltage is obtained from UNSW B+ after being routed through current-sense resistor R150 in the power control circuit. The output power of the module is controlled by varying the DC gate bias on U110 pin 2 (VGG). 5.3.2 Antenna Switch The antenna switch consists of two pin diodes, D120 and D121. In the receive mode, both diodes are off. Signals applied at the antenna or at jack J140 are routed, via the harmonic filter, through network C122-C124 and L121, to the receiver input. In the transmit mode, Q170 is on and TXB+ is present, forward-biasing both diodes into conduction. The diode current is 50 mA, set by R120-R122. The transmitter RF from U110 is routed through D120, and via the harmonic filter to the antenna jack. D121 conducts, shunting RF power and preventing it from reaching the receiver. L121 is selected to appear as a 1/4 wave at VHF, so that the low impedance of D121 appears as a high impedance at the junction of D120 and the harmonic filter input. This provides a high series impedance and low shunt impedance divider between the power amplifier output and receiver input. 5.3.3 Harmonic Filter The harmonic filter consists of components C130-C136 and L130-L132. The harmonic filter is a seven-pole elliptical low-pass configuration, optimized for low insertion loss, with a 3 dB frequency of approximately 210 MHz and typically less than 0.8 dB insertion loss in the passband. Power Control Harmonic Filter Antenna Matching NetworkPower Amplifier Module U110Q100TX_INJ (From VCO)5TVDD VGG TX_ENA PWR_SET USWB+ RX_IN (To Receiver) Antenna SwitchJ140 Antenna Jack Antenna
June, 20056880309N62-C 5-4146-174 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry 5.3.4 Antenna Matching Network The harmonic filter presents a 50 Ω impedance to antenna jack J140. A matching network, made up of C140-C141 and L140, is used to match the antenna impedance to the harmonic filter. This optimizes the performance of the transmitter and receiver into the impedance presented by the antenna, significantly improving the antennas efficiency. 5.3.5 Power Control The power control circuit is a dc-coupled amplifier whose output is the dc gate bias voltage (VGG) applied to the two stages of the RF power amplifier U110. The output power of the transmitter is adjusted by varying the setting of the power-set DAC contained in the ASFICcmp IC (DACG, U451 pin 6). This PWR_SET voltage is applied to U150 pin 3. Stage U150-2 compares the voltage drop across current sense resistor R150 to the voltage drop across resistor R151 caused by current flow through Q150, and adjusts its output (pin 7) to maintain equal voltages at pins 5 and 6. Thus the current flow through Q150, and hence its emitter voltage, is proportional to the current drawn by stage U110, which is in turn proportional to the transmitter output power. The emitter voltage of Q150 is applied to U150 pin 2, where it is compared to the power set voltage PWR_SET at pin 3. The output of U150 pin 1 is divided by R110 and R111 and applied as a gate voltage to the power amplifier U110. By varying this gate voltage as needed to keep the voltages at U150 pins 2 and 3 equal, power is maintained at the desired setting. Excessive final current, for example due to antenna mismatch, causes a lowering of the voltage at U150 pin 6, an increased voltage at pin 2, and a lowering of the voltage at pin 1 and of the gate voltage VGG. This prevents damage to the final stage due to excessive current. 5.4 VHF Frequency Generation Circuitry The frequency generation system, shown in Figure 5-3, is composed of two circuit blocks, the Fractional-N synthesizer IC U201, the VCO/Buffer IC U251, and associated circuitry. Figure 5-4 shows the peripheral interconnect and support circuitry used in the synthesizer block, and Figure 5-5 details the internal circuitry of the VCOBIC and its interconnections to the surrounding components. Refer to the schematic to identify reference designators. The Fractional-N synthesizer is powered by regulated 5 V and 3 V provided by U310 and U330 respectively. 5 V is applied to U201 pins 13 and 30, and 3 V is applied to pins 5, 20, 34 and 36. The synthesizer in turn generates a super-filtered 4.5 V supply (VSF, from pin 28) to power U251. In addition to the VCO, the synthesizer also interfaces with the logic and ASFICcmp circuits. Programming for the synthesizer is accomplished through the microprocessor SPI_DATA_OUT, SPI_CLK, and SYNTH_CS (chip select) lines (U409 pins 100, 1 and 47 respectively). A logic high (3 V) from U201 pin 4 indicates to the microprocessor that the synthesizer is locked.
6880309N62-CJune, 2005 146-174 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry 5-5 Transmit modulation from the ASFICcmp (U451 pin 40) is applied to U201 pin 10 (MOD_IN). An electronic attenuator in the ASFICcmp adjusts overall transmitter deviation by varying the audio level applied to the synthesizer IC. Internally the audio is digitized by the Fractional-N synthesizer and applied to the loop divider to provide the low-port modulation. The audio is also routed through an internal attenuator for the purpose of balancing the low port and high port modulation and reducing the deviation by 6 dB for 12.5 kHz channels, and is available at U201 pin 41 (VCO_MOD). This audio signal is routed to the VCOs modulator. Figure 5-3. VHF Frequency Generation Unit Block Diagram 5.4.1 Fractional-N Synthesizer The Fractional-N synthesizer, shown in Figure 5-4, uses a 16.8 MHz crystal (Y201) to provide the reference frequency for the system. External components C201-C203, R202 and D201 are also part of the temperature-compensated oscillator circuit. The dc voltage applied to varactor D201 from U201 pin 25 is determined by a temperature-compensation algorithm within U201, and is specific to each crystal Y201, based on a unique code assigned to the crystal that identifies its temperature characteristics. Stability is better than 2.5 ppm over temperatures of -30 to 60 °C. Software- programmable electronic frequency adjustment is achieved by an internal DAC which provides a frequency adjustment voltage from U201 pin 25 to varactor D201. The synthesizer IC U201 further divides the 16.8 MHz signal to 2.1 MHz, 2.225 MHz, or 2.4 MHz for use as reference frequencies. It also provides a buffered 16.8 MHz signal at U201 pin 19 for use by the ASFICcmp. To achieve fast locking of the synthesizer, an internal adapt charge pump provides higher current at U201 pin 45 to quickly force the synthesizer within lock range. The required frequency is then locked by the normal mode charge pump at pin 43. A loop filter (C243-C245 and R243-R245) removes noise and spurs from the steering voltage applied to the VCO varactors, with additional filtering located in the VCO circuit. Both the normal and adapt charge pumps get their supply from the capacitive voltage multiplier made up of C221-C224 and D220-D221. Two 3 V square waves from U201 pins 14-15 provide the drive signals for the voltage multiplier, which generates 12.1 V at U201 pin 47. This voltage is filtered by C225-C228. Synthesizer U201VCOBIC U251 Voltage Multiplier Loop Filter To Mixer To PA Driver VCP Vmult1 Vmult2Aux3 MOD Out Modulating SignalRx VCO Circuit Tx VCO Circuit TRB 16.8 MHz Ref. Osc. Rx Out Tx Out Buffer Q280
June, 20056880309N62-C 5-6146-174 MHz VHF Theory Of Operation: VHF Frequency Generation Circuitry One of the auxiliary outputs of the synthesizer IC (AUX3, U201 pin 2) provides the TRB signal which determines the operating mode of the VCO, either receive or transmit. Figure 5-4. VHF Synthesizer Block Diagram 5.4.2 Voltage Controlled Oscillator (VCO) The VCOBIC (U251), shown in Figure 5-5, in conjunction with the Fractional-N synthesizer (U201) generates RF in both the receive and the transmit modes of operation. The TRB line (U251 pin 19) determines which oscillator and buffer are enabled. A sample of the RF signal from the enabled oscillator is routed from U251 pin 12 through a low pass filter, to the prescaler input of the synthesizer IC (U201 pin 32). After frequency comparison in the synthesizer, a resultant DC control voltage is used to steer the VCO frequency. When the PLL is locked on frequency, this voltage can vary between 3 V and 9 V. L251 and C251 further attenuate noise and spurs on the steering line voltage. In the receive mode, the TRB line (U251 pin 19) is low. This activates the receive VCO and the receive buffer of U251, which operate within the range of 190.85 to 218.85 MHz. The VCO frequency is determined by tank inductor L254, C253-C257, and varactor D251. The buffered RF signal at U251 pin 8 is further amplified by Q280 and applied as RX_INJ to the low-pass injection filter in the receiver front end circuit. In the transmit mode, U251-19 is driven high by U201 pin 2, enabling the transmit VCO and buffer. The 146-174 MHz RF signal from U251 pin 10 is applied as TX_INJ to the input of the transmitter circuit via matching network C290-C291 and L291. TX VCO frequency is determined by L264, C263- DATA CLK CEX MODIN V CC, 5V XTAL1 WARP PREIN VCP Reference Oscillator Voltage Multiplier Voltage Controlled Oscillator 2-Pole Loop Filter DATA (U401 Pin 100) CLOCK (U401 Pin 1) SYNTH_CS (U401 Pin 47) MOD IN (U451 Pin 40) +5V (U310 Pin 5)7 8 9 10 13,30 23 25 32 47 VMULT2 VMULT1BIAS1 SFOUTAUX3 IADAPTIOUTGND FREFOUTLOCK4 19 6,22,23,24 43 45 2 28 141540Filtered 5VSteering Line LOCK (U401 Pin 56) Prescaler InLO RF Injection TX RF Injection (First Stage of PA) FREF (U451 Pin 34) 39 BIAS241 +3V (U330 Pin 5) V DD, 3VMODOUTU201 Low Voltage Fractional-N Synthesizer 5,20,34,36 TRB VCO Mod